Chapter 2 Procedure for Designing Fractional-Order Filters

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1 Chapter Procedure for Designing Fractional-Order Filters. Introduction Fractional-order differentiation and integration topologies offer attractive features in various interdisciplinary applications. A typical application is the substitution of conventional integer order parts of a system with the fractional-order parts, respectively, where the existence of derivation/integration has a decisive position, and offers important benefits. Also, they are able to be used in order to realize one of the most important circuits in fractional-order theory, which is the fractal device. On the other hand, fractional-order filters, offer more precise control of the attenuation gradient, which is an efficient feature in biomedical engineering. Fractional-order filters, differentiators, and integrators, will be presented in a systematic way that describes the most important features of these structures; realizing such circuits through the utilization of a general form enabling the capability of realizing different kind of circuits by the same topology, which is very important from the flexibility point of view. All the above will be performed through the utilization of the second-order CFE, which is an efficient tool, in terms of accuracy and circuit complexity, and has been described in Chap. in detail. As a consequence, the main benefit of this procedure is that having available the design equations, which are expressed through integer-order functions, the capability of realizing these types of functions utilizing different ways of circuit design could be achieved. The Author(s) 07 G. Tsirimokou et al., Design of CMOS Analog Integrated Fractional-Order Circuits, SpringerBriefs in Electrical and Computer Engineering, DOI 0.007/ _ 3

2 4 Procedure for Designing Fractional-Order Filters. Fractional-Order Generalized Filters (Order ) Integrators and differentiators are very useful building blocks for performing signal conditioning in biomedical applications. Also, they are employed for realizing oscillators, impedance emulators, and in control systems. Fractional-order digital implementations of such circuits have been already published in the literature [ 5]. The utilization of the second-order expressions of CFE is an appropriate tool for realizing fractional-order differentiators and integrators in order to approximate the variable (τs) ug the formula given in (.). In case that ¼, this transfer function represents a differentiator, while for ¼ an integrator. In the range (0 < < ), this element may generally be considered to represent a fractionalorder differentiator, while in the range ( < < 0), a fractional-order integrator. ðτs Þ ¼ 0ðτsÞ þ ðτsþþ ðτsþ ð:þ þ ðτsþþ 0.. Fractional-Order Differentiator The transfer function, as well as the magnitude response of an integer-order differentiator is given by the formula H(s) ¼ τs, and H() ¼ /, respectively. The unity gain frequency is ¼ /τ, where τ is the corresponding time-constant. In addition the phase response is constant and equal to π/. Thus, the transfer function of a fractional-order differentiator will be given by (.) as Hs ðþ¼ðτsþ ð:þ where (0 < < ) is the order of the differentiator. The magnitude response is given as H() ¼ (/ ), from which is obvious that the unity gain frequency has the same expression as in the case of its integer-order counterpart. Also, in this case the phase response is constant but equal to / predicting the total reliance of phase from the fractional-order [6]. Comparing the above expressions of magnitude responses of fractional and integer-order differentiator, it is obvious that at the same frequency the fractionalorder differentiator realizes a gain smaller than that achieved by its integer-order counterpart. As a result, with the substitution of (.) into (.), the transfer function of fractional-order differentiator is expressed as shown in (.3), where i (i ¼ 0,, ) is given by (.6) or (.0). Their values depend on the type of the approximation that has been utilized. H diff ðþ¼ s o s þ τ s þ τ τ s þ s þ o τ ð:3þ

3 . Fractional-Order Generalized Filters (Order ) 5.. Fractional-Order Integrator The transfer function of a fractional-order lossless integrator could be written as shown in (.4), while the magnitude response is given as H() ¼ ( /), where ¼ /τ is the unity gain frequency of the integrator. Its phase response will be a constant equal to /. Hs ðþ¼ ðτsþ ð:4þ The corresponding expressions of its integer-order counterpart with the same unit gain frequency will be H() ¼ / and π/, respectively. By ug the same order of approximation as in the case of fractional-order differentiator, the transfer function in (.4) could be approximated as it is demonstrated in (.5), where i (i ¼ 0,,) is given by (.6) or (.0). H int ðþ¼ s 0 s þ 0 τ s þ τ τ s þ 0 τ s þ 0 ð:5þ Taking into account that the transfer function in (.3) and (.5) have an integerorder form, they could be easily performed either by the typical functional block diagram (FBD) of the follow-the-leader-feedback (FLF) topology depicted in Fig..a, or the inverse-follow-the-leader, multi-feedback (IFLF) topology given in Fig..b, where the notation (xg i ) implies a scaled replica of the corresponding output. The transfer function is that in (.6). Comparing (.3) and (.5) with (.6) Fig.. FBD for realizing fractional-order differentiator/integrator of order ug (a) FLF current-mode topology, (b) IFLF voltage-mode topology

4 6 Procedure for Designing Fractional-Order Filters Table. Design expressions of time-constants τ i for approximating fractional-order differentiator, lossless integrator with unity gain frequency ( ¼ /τ) Transfer function τ τ H(s) ¼ (τs) τ τ 0 Hs ðþ¼ 0 ðτsþ τ τ Table. Design expressions of gain factors G i for approximating fractionalorder differentiator, lossless integrator with unity gain frequency ( ¼ /τ) Transfer function G G G 0 H(s) ¼ (τs) 0 Hs ðþ¼ ðτsþ the derived expressions of time-constants τ i and gain factors G i (i ¼ 0,,) are as summarized in Tables., and., respectively. Hs ðþ¼ G s þ G τ s þ G 0 τ τ s þ τ s þ τ τ ð:6þ.3 Fractional-Order Generalized Filters (Order ) Fractional-order filters of order where (0 < < ) will be presented and some of the most critical frequencies have been derived in order to be fully characterized. From the stability point of view, this system is stable if and only if > 0 and <, while it will oscillate if and only if > 0 and ¼ ; otherwise it is unstable. The derived frequency responses of filters of order exhibit a stopband attenuation proportionate to the fractional-order, which offers a more precise control of the attenuation gradient compared to the attenuation offered in the case of integer-order filters of order n, which is 6n db/oct [6 9]. Thus, low-pass, high-pass, band-pass, and all-pass filters of order will be presented. Also, ug a general topology, all the aforementioned type of filters could be realized, ug the same core. The most important critical frequencies that will be studied are the following: p is the frequency at which the magnitude response has a maximum or a minimum and is obtained by solving the equation d d jhj ð Þj ¼ p ¼ 0 p h is the half-power frequency at which jhj ð Þj ¼h ¼ jhj ð Þj ¼p = ffiffi rp is the right-phase frequency at which the phase H( j) ¼π/ It should be mentioned that rp exists only if >.

5 .3 Fractional-Order Generalized Filters (Order ) 7.3. Fractional-Order Low-Pass Filter (FLPF) The transfer function of a FLPF is that in (.7), where κ is the low-frequency gain and /τ the pole frequency. The magnitude and phase response are given by (.8). The critical frequencies are summarized in Table.3, where the magnitude and phase values are also given. Ug (.8), the expressions for the h and the corresponding phase are these in (.9). Hs ðþ¼κ s þ ¼ κ o ðτsþ þ κ jhj ð Þj ¼ r ffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ þ 0 HðjÞ ¼ κ tan B A þ ð:7þ ð:8aþ ð:8bþ In addition, the peak and right-phase frequency are found as p ¼ [ (/ )] /, and rp ¼ /[ (/)] /. The stopband attenuation gradient of the fractional-order low-pass filter order is equal to 6 db/oct. rffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi h ¼ þ = ð:9aþ 0 HðjÞ ¼h ¼ κ tan B qffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi A ð:9bþ þ þ.3. Fractional-Order High-Pass Filter (FHPF) The transfer function of a FHPF with high-frequency gain κ and pole frequency /τ is that in (.0). The magnitude response and phase response are given by (.), while all the critical frequencies are summarized in Table.4. Table.3 Magnitude and phase values at important frequencies for the FLPF jh( j)j jh( j)j!0 κ κ κ 4 κ /4! 0 κ /! h κ p ffiffi κ tan ð pffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi Þ ð Þþ ð Þ þ

6 8 Procedure for Designing Fractional-Order Filters Table.4 Magnitude and phase values at important frequencies for the FHPF jh( j)j jh( j)j!0 0 κ þ / κ κ þ /4 4! κ κ 0 h κ p ffiffiffi κ þ tan B qffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi A þ Hs ðþ¼κ s s þ ¼ κ ðτs o ðτsþ þ κ jhj ð Þj ¼ rffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ þ 0 HðjÞ ¼ κ þ = tan B A þ Þ ð:0þ ð:aþ ð:bþ The corresponding expressions for the h and phase at this frequency are given by (.). In addition, the peak, and right-phase frequency are found as p ¼ / [ (/)] /, and rp ¼ [ (/)] /. From these expressions it is seen that both p and rp exist only if >. Also, the stopband attenuation gradient of the fractional-order high-pass filter of order is equal to þ6 db/oct. rffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi h ¼ þ þ = ð:aþ 0 HðjÞ ¼h ¼ κ þ tan B ffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi q A ð:bþ þ.3.3 Fractional-Order Band-Pass Filter (FBPF) The transfer function of a FBPF with peak-frequency gain κ and pole frequency /τ is that in (.3), where the magnitude and phase is as shown in (.4a) and (.4b), respectively. In order to obtain a FBPF response, the condition > should be fulfilled. All the critical frequencies are summarized in Table.5.

7 .3 Fractional-Order Generalized Filters (Order ) 9 Table.5 Magnitude and phase values at important frequencies for the FBPF H( j) H( j)!0 0 κ þπ/ p ¼ κ þ [( )π]/4 4! o κ þ [( )π]/ Hs ðþ¼κ s s þ ¼ κ ðτs o ðτsþ þ κ jhj ð Þj ¼ rffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ þ 0 HðjÞ ¼ κ þ π= tan B A þ Þ ð:3þ ð:4aþ ð:4bþ The peak frequency ( p ), calculated from the condition d d jhj ð Þj ¼ p ¼ 0, is given by (.5). In the case that ¼, then p ¼. Obviously, for ¼, the transfer function in (.3) is modified and corresponds to the already known FHPF. 8 h qffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi i9 < ð Þþ þ 4ð Þtan = p ¼ : ð Þ ; = ð:5þ All the critical frequencies are summarized in Table.5, where the magnitude and phase values are also given. It should be mentioned that the stopband attenuation gradient at the upper frequencies is 6( ) db/oct, while for the lower frequencies is þ6 db/oct, offering the capability of realizing a low-q band pass filter with different slopes of the stopband attenuations. In case that ¼, the slope is then equal to 6 db/oct, and þ6 db/oct, respectively..3.4 Fractional-Order All-Pass Filter (FAPF) A FAPF with gain κ and pole frequency /τ is described through the transfer function given by (.6) Hs ðþ¼κ s s þ ¼ κ ðτsþ o ðτsþ þ ð:6þ

8 0 Procedure for Designing Fractional-Order Filters Table.6 Magnitude and phase values at important frequencies for the FAPF H( j) H( j)!0 0 κ þ π p ¼ κ þ π/ κ tan 4 h κ κ Its frequency behavior is described by (.7) vffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ jhj ð Þj ¼ κu t þ þ ð:7aþ It can be easily seen here that p ¼ rp ¼, as well as that at this frequency a minima occurs if < and a maxima occurs if > while the magnitude remains flat when ¼ (i.e., classical integer-order all-pass filter). All the critical frequencies are summarized in Table.6 where the magnitude and phase values are also given. HðjÞ¼ κ 0 0 tan C A tan B A þ ð:7bþ.3.5 Design Equations for Generalized Filters of Order Taking into account that the transfer functions of all the aforementioned fractionalorder filters are expressed through the variables (τs) and/or (τs), and the fact that they are not realizable, they should be approximated by appropriate expressions. Ug the second-order expressions of the CFE given by (.) and substituting into (.7), (.0), (.3), and (.6), the derived transfer functions are given in (.8). The coefficient i corresponds to the approximation of variable (τs), while b i to the variable (τs). Comparing the transfer functions of the FLPF and FHPF, the numerator in H HP (s) is easily derived through the substitution: 0 $ in the numerator of H LP (s). Inspecting the transfer functions of FLPF, FHPF, and FAPF it is concluded that all of them have the same form. Consequently, they could be realized by the same topology just by changing the coefficient values. A suitable solution for this purpose has been already given in Fig.., where the realized transfer function is that given in (.6).

9 .3 Fractional-Order Generalized Filters (Order ) H LP H HP κ ðþ¼ s s þ τ s þ 0 τ ð:8aþ 0 þ s þ τ s þ τ 0 þ κ ðþ¼ s 0s þ τ s þ τ 0 þ s þ τ s þ τ 0 þ ð:8bþ H BP H AP ðþ¼κ s 0 0 þ 0 þ s τ s þ 0 þ τ s þ τ κ ðþ¼ s s þ τ s þ 0 τ b 0s þ b τ s þ b τ 0 þ s þ τ s þ b τ s þ b τ s þ b 0 b τ b ð:8cþ ð:8dþ Comparing the coefficients of (.6) with those of FLPF, FHPF, and FAPF in (.8), it is derived that the design equations about the time-constants of fractionalorder low-pass, high-pass, and all-pass filters of order are those in (.9). The corresponding design equations for the scaling factors G i (i ¼ 0,, ) are summarized in Table.7. τ ¼ 0 þ τ ð:9aþ τ ¼ þ 0 τ ð:9bþ With regards to the FBPF realization, a possible solution is the FBD in Fig.., where H (s) and H (s) are mentioned filter blocks as that in Fig.., which realize the transfer function in (.6). The expressions for time-constants τ ij, where (i ¼, ) is the number of time-constants of each state, and ( j ¼, ) is the number of state, are given by (.0). The time-constants of the first stageτ i have the same values as in (.9). The corresponding design equation for the scaling factors G ij (i ¼ 0,, and j ¼, ) of both stages are also summarized in Table.7. Table.7 Values of scaling factors G ij for realizing FLPF, FHPF, FAPF, and FBPF of order in Figs., and. Filter G G G 0 FLPF κ κ 0 κ þ 0 þ 0 FHPF 0 κ κ κ þ 0 0 þ FAPF FBPF ( j ¼ ) κ 0 0 κ 0 þ 0 þ 0 κ 0 κ κ þ 0 þ 0 ( j ¼ ) b 0 b b b 0

10 Procedure for Designing Fractional-Order Filters Fig.. FBD for realizing FBPF of order ug (a) current mode topology, (b) voltage mode topology τ ¼ 0 þ τ, τ ¼ b b τ τ ¼ þ 0 τ, τ ¼ b b 0 τ ð:0aþ ð:0bþ.4 Fractional-Order Generalized Filters (Order þ ) Although, fractional-order filters constitute a small portion of fractional-order calculus, they have gained a growing research interest offering important features especially on behavior of the attenuation gradient. The stopband attenuation of integer order filters has been limited to increments based on the order n, but ug the fractional Laplacian operator attenuations between these integer steps can be achieved creating fractional step filter of order (n þ ), where is the fractional step between integer orders n and n þ and is therefore limited to (0 < < ). The derived frequency responses of filters of order þ exhibit a stopband attenuation equal to 6( þ ) db/oct, which offer a more precise control of the attenuation gradient compared to the attenuation offered in the case of integer-order filters of order n, which is 6n db/oct [6 9]. In this section, low-pass, high-pass, bandpass, and band-stop filters of order þ are presented, and some of the most critical frequencies ( p, h ) are also given in order to be fully characterized. Finally, ug the CFE method, the derived design equations results into a general topology, from which all the aforementioned type of filters could be realized..4. Fractional-Order Low-Pass Filter (FLPF) According to the analysis provided in [8], the direct realization of a fractional filter of the order n þ is stable in the case that n þ <. Therefore, only fractional filters of the order þ offer realizations without stability problem. The transfer function of a þ -order fractional low-pass filter is given by

11 .4 Fractional-Order Generalized Filters (Order þ ) 3 Hs ðþ¼ κ s þ þ κ ð:þ where the low-frequency gain is equal to κ /κ, and the 3 db frequency is given by (.) 3dB ¼ κ þ þ Þπ þ Þπ " r ffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi! # þ ð:þ The obtained frequency responses suffer from the presence of an undesired peaking equal to κ /κ [(( þ )π/)] at the frequency p ¼ [ κ ( þ )π/] (þ). In order to overcome this problem, the modified transfer function given by (.3), which intends to approximate the all-pole Butterworth response, is introduced, where an extra term equal to κ 3 s has been added in the denominator of the transfer function in (.). The transfer function of a FLPF with low-frequency gain κ /κ and pole frequency ¼ /τ is that in (.3) κ Hs ðþ¼ ðτsþ þ ðτsþ ð:3þ þ κ The factors κ i (i ¼,, 3) are calculated by appropriate expressions, in order to minimize the error in the frequency response [9]. Such expressions are recalled in (.4). κ ¼ κ ¼ 0:937 þ 0:76 κ 3 ¼ :068 þ 0:6 þ 0:334 ð:4þ The magnitude response and phase response are given by (.5) as jhj ð Þj ¼ vffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ ð Þ þ þ κ u t o κ κ 3 þ κ 0 þ HðjÞ ¼ κ tan þ κ3 B þ A þ κ3 þ κ The peak frequency ( p ) is calculated solving the following equation: þ þ ð Þ p κ ð þ Þ p þκ p 3 þ κ κ 3 ¼ 0 which is derived from (.5) under the condition d d jhj ð Þj ¼ p ¼ 0. κ ð:5aþ ð:5bþ ð:6þ

12 4 Procedure for Designing Fractional-Order Filters The half-power ( 3 db) frequency ( h ), defined as the frequency where there is a drop of the passband gain, is calculated solving the following equation: þ ð Þ þ h κ h þ κ κ h 3 κ ¼ 0 h ð:7þ Also, the stopband attenuation gradient of the þ fractional-order low-pass filter is equal to 6( þ ) db/oct..4. Fractional-Order High-Pass Filter (FHPF) The transfer function of a FHPF is given by (.8) κ s þa Hs ðþ¼ ðτsþ þa ðτsþ a ð:8þ þ κ The magnitude response and phase response are given by (.9). jhj ð Þj ¼ vffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ ð Þ þ þ κ u t o κ κ 3 þ κ HðjÞ¼ κ þ ð þ Þπ 0 þ tan B þ A þ κ κ þ ð:9aþ ð:9bþ The peak frequency ( p ) is calculated solving the equation given in (.30), which is derived from (.9) under the condition d d jhj ð Þj ¼ p ¼ 0. Þ þ p κ 3 ð þ Þκ κ p 3 κ ð þ p ð þ Þκ ¼ 0 ð:30þ The half-power ( 3 db) frequency ( h ), defined as the frequency where there is a drop of the passband gain, is calculated solving the equation given in (.3).

13 .4 Fractional-Order Generalized Filters (Order þ ) 5 Also, the stopband attenuation gradient of the fractional-order high-pass filter order þ is equal to þ6( þ ) db/oct. þ ð Þ þ h þ κ h κ 3 κ κ h 3 κ ¼ 0 h ð:3þ.4.3 Fractional-Order Band-Pass Filter (FBPF) The transfer function of a FBPF is given by (.3) κ 3 ðτsþ a Hs ðþ¼κ ðτsþ þa ðτsþ a ð:3þ þ κ Ug (.3), the magnitude and phase response are given as κ κ 3 jhj ð Þj ¼ vffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ ð Þ þ þ κ o u o t κ κ 3 þ κ HðjÞ ¼ κ κ 3 þ 0 þ tan B þ A þ κ ð:33aþ ð:33bþ The peak frequency ( p ) is calculated solving the equation given in (.34), which is derived from (.33a) under the condition d d jhj ð Þj ¼ p ¼ 0. þ ð p κ κ 3 Þ ð p Þκ p þ κ ¼ 0 ð:34þ The half-power ( 3 db) freaquencies ( h, h ) are defined as the frequencies where there is a drop of the passband gain. The quality factor of the filter (Q) is calculated solving the following equation: p Q ¼ h h ð:35þ where h and h are the upper and lower half-power frequencies, respectively.

14 6 Procedure for Designing Fractional-Order Filters Also, the stopband attenuation gradient at the upper frequencies is 6 db/oct, while for the lower frequencies is þ6 db/oct, offering the capability of realizing a FBPF with the stopband attenuation being varied at the lower frequencies..4.4 Fractional-Order Band-Stop Filter (FBSF) A FBSF has the transfer function given by (.36) ðτsþ þ þ κ Hs ðþ¼κ ðτsþ þ ðτsþ ð:36þ þ κ The magnitude response and phase response are given by (.37), while the peak frequency ( p ) is calculated from (.37) under the condition d d jhj ð Þj ¼ p ¼ 0. The half-power ( 3 db) frequencies ( h ) are calculated from the condition that at these frequencies there is a drop of the passband gain. vffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ ð Þ þ κ þ κ jhj ð Þj ¼ κ þ ð Þ þ þ κ þ κ u 3 o t κ κ 3 o þ κ 0 þ HðjÞ ¼ k þ tan B þ A þ k 0 þ tan þ k B 3 þ A þ k 3 þ k The quality factor of the filter is calculated according to the formula: ð:37aþ ð:37bþ p Q ¼ h h ð:38þ where h and h are the upper and lower half-power frequencies, respectively..4.5 Design Equations for Generalized Filters of Order þ The realization of the fractional-order filters of order þ has been achieved in a similar way as in the previous section, where the approximation of variable (τs)

15 .4 Fractional-Order Generalized Filters (Order þ ) 7 Fig..3 FBD for realizing FLPF, FHPF, FBPF, and FBSF of order þ ug (a) current mode topology, (b) voltage mode topology has been performed through the utilization of the second-order expressions of the CFE given by (.) and substitution into (.3), (.8), (.3), and (.36). As a result, the derived transfer functions are that in (.39). Inspecting the transfer functions of FLPF, FHPF, FBPF, and FBSF, it is concluded that all of them have the same form. Consequently they could be realized by the same topology just by changing the coefficient values. A suitable solution for this purpose is depicted in Fig..3, where a typical (FBD) of a (FLF) topology and an (IFLF) topology are given in Fig..3a and Fig..3b, respectively. The realized transfer function is that given in (.40). Hþ LP ðþ¼κ s τ s þ τ s þ 0 τ 3 0 s 3 þ 3 þ κ 0 0 τ s þ 6 þ κ 0 τ s þ κ þ κ τ 3 Hþ HP ðþ¼κ s 0 s 3 þ s þ s 0 s 3 þ 3 þ κ 0 0 τ s þ 6 þ κ 0 τ s þ κ þ κ τ 3 Hþ BP ðþ¼κ s κ 3 0 τ s þ τ s þ τ 3 0 s 3 þ 3 þ κ 0 0 τ s þ þ κ 0 τ s þ κ 0 0 τ 3 ð:39aþ ð:39bþ ð:39cþ

16 8 Procedure for Designing Fractional-Order Filters Table.8 Values of scaling factors G i (i ¼ 0,...,3) for realizing fractional low-pass, high-pass, band-pass, and band-stop filter in Fig..3 of order þ Filter G 3 G G G 0 FLPF 0 κ κ κ 0 κ 0 þ þ ðκ Þ κ 0 FHPF κ κ κ 0 κ 0 þ þ ðκ Þ FBPF 0 κ κ 3 0 κ κ 3 κ κ 3 κ 0 þ þ ðκ Þ κ 0 FBSF κ κ ð þ κ Þ κ ð þ κ Þ κ κ 0 κ 0 þ þ ðκ Þ κ 3 þ κ 0 Hþ BS ðþ¼κ s 0s 3 þ ð þ κ Þ τ s þ ð þ κ Þ τ s þ ðκ 0 Þ τ s 3 þ þ κ 0 0 τ s þ 6 þ κ 0 τ s þ κ 4 3 þ κ 0 0 τ 3 Hs ðþ¼ G 3s 3 þ G τ s þ G τ τ s þ G 0 s 3 þ τ s þ τ τ s þ τ τ τ 3 τ τ τ ð:39dþ ð:40þ Comparing the coefficients of (.40) with these of FLPF, FHPF, and FBSF it is derived that the design equations about the time-constants τ i (i ¼,, 3) of all the filters are given in (.4). 0 τ ¼ τ ð:4aþ κ 0 þ τ ¼ κ 0 þ κ þ τ ð:4bþ τ 3 ¼ κ þ κ 0 τ ð:4cþ The corresponding design equations for the scaling factors G i (i ¼ 0,...,3) are summarized in Table.8..5 Fractional-Order Generalized Filters (Order þ ) The utilization of two different orders and, where þ < and, > 0 provides one more degree of freedom, which is able to vary, in order to realize fractional order filters of order þ. Such kind of filters exhibit a stopband attenuation which is proportionate to the fractional-order,. In this section,

17 .5 Fractional-Order Generalized Filters (Order þ ) 9 FLPF, FHPF, FBPF, and FBSF of order þ are presented, and some of the most critical frequencies have been derived in order to be fully characterized. The most important critical frequencies that will be presented are the following: p is the frequency at which the magnitude response has a maximum or a minimum and is obtained by solving the equation d d jhj ð Þj ¼ p ¼ 0 h is the half-power frequency at which the power drops to half the passband p power, i.e., jhj ð Þj ¼h ¼ jhj ð Þj ¼p = ffiffiffi Also, ug a general topology, all the aforementioned type of filters could be realized and this is very important from the flexibility point of view..5. Fractional-Order Low-Pass Filter (FLPF) The transfer function of the FLPF of order þ is given by Eq. (.4) κ Hs ðþ¼ ðτsþ þ ðτsþ ð:4þ þ κ The magnitude response and phase response are given by (.43). The half-power ( 3 db) frequency ( h ), defined as the frequency where there is a drop of the passband gain, is calculated solving the equation given by (.44), which is derived taking into account that the maximum gain of the filter is κ /κ. Also, the stopband attenuation gradient of the fractional-order low-pass filter of order þ is equal to 6( þ ) db/oct. jhj ð Þj ¼ vffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi ðþþ þ þ κ3 þ κ u þ ð þ Þπ t þκ π þ κ κ 3 κ ð:43aþ HðjÞ ¼ κ 0 þ ð þ Þπ tan π B þ ð þ Þπ π A þ κ ðþþ þ h þ κ3 h þ þ κ h ð þ Þπ þ κ h 3 þ κ κ h π 3 κ ¼ 0 ð:43bþ ð:44þ

18 30 Procedure for Designing Fractional-Order Filters.5. Fractional-Order High-Pass Filter (FHPF) The transfer function of a HLPF with maximum gain equal to κ /κ is that in (.45) Hs ðþ¼ κ ðτsþ þ ðτsþ þ ðτsþ ð:45þ þ κ The magnitude response and phase response are given by (.46) as jhj ð Þj ¼ vffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi ðþþ þ þ κ3 þ κ þ u þ ð þ Þπ t þκ π þ κ κ 3 Hðj κ þ ð:46aþ Þ ¼ κ þ ð þ Þπ 0 þ ð þ Þπ tan π B þ ð þ Þπ π A þ κ ð:46bþ The half-power ( 3 db) frequency ( h ), defined as the frequency where there is a drop of the passband gain, is calculated solving the equation given in (.47). Also, the stopband attenuation gradient of the fractional-order high-pass filter of order þ is equal to 6( þ ) db/oct. ðþþ þ h κ3 h þ κ h ð þ Þπ ð:47þ κ h 3 κ κ h π 3 κ ¼ Fractional-Order Band-Pass Filter (FBPF) The transfer function of a FBPF is κ 3 ðτsþ Hs ðþ¼κ ðτsþ þ ðτsþ ð:48þ þ κ

19 .5 Fractional-Order Generalized Filters (Order þ ) 3 Ug (.48), the magnitude and phase response is expressed through the following equations: κ κ 3 jhj ð Þj ¼ vffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi ðþþ þ þ κ3 þ κ þ u þ ð þ Þπ t þκ π þ κ κ 3 ð:49aþ HðjÞ ¼ κ κ 3 þ π 0 þ ð þ Þπ tan π o B þ ð þ Þπ π A þ κ ð:49bþ The peak frequency ( p ) is calculated solving the equation given in (.49), which is derived from (.48) with the condition: d d jhj ð Þj ¼ p ¼ 0. ðþþ þ p þ p κ3 þ þ ð Þκ p ð þ Þπ k k p π 3 k ¼ 0 The quality factor of the filter is calculated according to the formula: ð:50þ p Q ¼ h h ð:5þ where h and h are the upper and lower half-power frequencies, respectively. Also, the stopband attenuation gradient at the upper frequencies is 6 db/oct, while for the lower frequencies is þ6 db/oct, offering the capability of realizing a FBPF with the stopband attenuation being varied in both frequency regions..5.4 Fractional-Order Band-Stop Filter (FBSF) A FBSF has the transfer function given by (.5). ðτsþ aþ þ κ Hs ðþ¼κ ðτsþ aþ ðτsþ ð:5þ þ κ

20 3 Procedure for Designing Fractional-Order Filters vffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi ðaþþ aþ h i þ κ ðþþπ þ κ jhj ð Þj ¼ κ ðþþ þ þ κ3 þ ð:53aþ κ u þ ð þ Þπ t þκ π þ κ κ 3 0 þ ð þ Þπ HðjÞ ¼ κ tan B þ ð þ Þπ A þ κ 0 þ ð þ Þπ π tan B þ ð þ Þπ π A þ κ ð:53bþ The magnitude response and phase response are given by (.53), while the peak frequency ( p ) is calculated from (.53) under the condition d d jhj ð Þj ¼ p ¼ 0. The half-power ( 3 db) frequencies ( h ) are calculated ug the fact that at these frequencies there is a drop of the passband gain which is equal to κ. The quality factor of the filter is calculated from (.5)..5.5 Design Equations for Generalized Filters of Order þ Utilizing the second-order expression of the CFE given by (.) and substituting into (.4), (.45), (.48), and (.5) the derived transfer function for FLPF, FHPF, FBPF, and FBSF is the following: H þ ðþ¼ s κ D 4 N 4 s 4 þ N 3 τ s3 þ N τ s þ N τ s þ N 3 0 h τ 4 i ð:54þ s 4 þ D 3 D 4 τ s3 þ D D 4 τ s þ D D 4 τ s þ D 3 0 D 4 τ 4 where the coefficients of the denominator D i and nominator N i (i ¼,...,4) have been defined in (.55), and Table.9, respectively. D 0 b 0 b þ κ 0 b 0 D b þ b b 0 b þ κ b 0 þ κ 0 b D 0 b þ 0 b þ b 0 b b 0 b 0 þκ b 0 þ κ b þ κ 0 b D 3 0 b þ b 0 b b 0 þ κ b þ κ b D 4 0 b 0 b 0 þ κ b ð:55þ

21 .5 Fractional-Order Generalized Filters (Order þ ) 33 Table.9 Values of the coefficients of the nominator N i (i ¼,...,4) in (.54) for realizing FLPF, FHPF, FBPF, and FBSF of order þ Filter N 4 N 3 N N N 0 FLPF b b þ b b0 þ b þ 0b b0 þ 0b 0b0 FHPF 0 b 0 b 0 þ 0 b 0 b þ b þ b 0 b þ b b FBPF κ 3 b 0 κ 3 ( b þ b 0 ) κ 3 ( b þ b þ 0 b 0 ) κ 3 ( b þ 0 b ) κ 3 0 b FBSF b 0 þ κ b 0 0b þ b0 0b þ b b þ b b þ κ 0 b 0 þκb þ κb þb0 þ κb0 þκb0 þ κ0b þκb þ κ0b

22 34 Procedure for Designing Fractional-Order Filters Fig..4 FBD for realizing fractional FLPF, FHPF, FBPF, and FBSF of order þ ug (a) current mode topology, (b) voltage mode topology Comparing the transfer functions of the FLPF and FHPF, it is easily derived that the numerator in H HP (s) is derived through the substitution 0 $ and b 0 $b in the numerator of H LP (s). In a similar way, the numerator in H BP (s) is derived through the substitution b 0 $b in the numerator of H LP (s) multiplied by the factor κ 3. Inspecting the transfer function given in (.54), it is easily concluded that all of them were expressed by the same form, and consequently they could be realized by the same topology just by changing the coefficient values. A suitable solution for this purpose is depicted in Fig..4, where a typical FBD of a FLF topology and an IFLF topology are given in Fig..4a and Fig..4b, respectively. The realized transfer function is that given in (.56). Comparing the coefficients of (.54) with those in (.56), it is derived that the design equations about the time-constants τ j ( j ¼,...,4) of all the filters and the corresponding design equation for the scaling factor G i (i ¼ 0,...,4) are given in (.57) and (.58), respectively. Hs ðþ¼ G 4s 4 þ G 3 τ s 3 þ G τ τ s þ G τ τ τ 3 s þ G 0 s 4 þ τ s 3 þ τ τ s þ τ τ τ 3 s þ τ τ τ 3 τ 4 τ j ¼ D 5 j D 4 j τ τ τ τ 3 τ 4 ð:56þ ð:57þ G i ¼ κ N i D i ð:58þ where the values of the coefficients N i are those given in Table.9, and depend on the desired filter function.

23 .6 Fractional-Order Filters of Order n þ 35.6 Fractional-Order Filters of Order n þ The procedure for realizing a high-order fractional filter of order n þ will be studied, where n is the integer-order of the filter and corresponds to values n, and is the order of the fractional part of the filter where (0 < < ). Such kind of filters exhibits stopband attenuation equal to 6(n þ ) db/oct. The attenuation offered in the case of integer-order filters of order n, which is 6n db/oct. Thus, low-pass, high-pass, band-pass, and band-stop filters of order n þ are presented, and two different design procedures are followed in order to realize these kinds of filters. According to [8, 9], the realization of a fractional-order filter of order n þ with Butterworth characteristics could be performed through the utilization of the polynomial ratio given by (.59) H nþ ðþ¼ s H þðþ s B n ðþ s ð:59þ where H þ (s) is the transfer function given by (.3), (.8), (.3), (.36) for realizing a FLPF, FHPF, FBPF, and FBSF, respectively, and B n (s) is the corresponding Butterworth polynomial of order n-. Some of these polynomials are the following: B ðþ¼s s þ p B ðþ¼s s þ ffiffiffi s þ B 3 ðþ¼ s ðs þ Þðs þ s þ Þ B 4 ðþ¼ s ðs þ 0:7654s þ Þðs þ :8478s þ Þ B 5 ðþ¼ s ðs þ Þðs þ 0:68s þ Þðs þ :68s þ Þ ð:60þ The gain response of the (n þ ) filter is that given in (.6) jh nþ ðþj ¼ sffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ ð Þ ðn Þ þ þ ð:6þ Performing a routine algebraic procedure it is derived from (.6) that ðnþþ h þ h n ð Þ þ þ ð Þ h ¼ 0 ð:6þ

24 36 Procedure for Designing Fractional-Order Filters.6. Design Equations for Generalized Filters of Order n þ Utilizing the second-order expression of the CFE given by (.) and ug the expressions in (.39), then from (.59) it is obtained that the general forms of the transfer functions will be the following: Hnþ LP ðþ¼κ s 0 Hnþ HP ðþ¼κ s Hnþ BP ðþ¼κ s κ 3 0 Hnþ BS ðþ¼κ s 0 0 τ s þ n τ s þ nþ 0 τ nþ s nþ þ nþ τ snþ þþ τ s þ nþ 0 τ nþ ð:63aþ 0 τ s 3 þ τ s þ n τ s nþ 0 s nþ þ nþ τ snþ þþ τ s þ nþ 0 τ nþ ð:63bþ 0 τ s þ n τ s þ nþ τ nþ ð:63cþ s nþ þ nþ τ snþ þþ τ s þ nþ 0 τ nþ τn s3 þ ð þ κ Þ τ ns þ ð þ κ Þ τ nþs þ κ 0 s nþ þ nþ τ snþ þþ τ nþs þ 0 τ nþ τ nþ ð:63dþ where κ (κ ¼ 0,,...,n þ ) is a function of i, which is a result of multiplication of the denominator of H þ (s) in (.39) and the coefficients of B n (s). Inspecting the transfer functions of FLPF, FHPF, FBPF, and FBSF, it is concluded that all of them have the same form. Consequently they could be realized by the same topology just by changing the coefficient values. A suitable solution for this purpose is depicted in Fig..5, where a typical FBD of a FLF topology and an IFLF topology are given in Fig..5a and Fig..5b, respectively. Fig..5 FBD for realizing FLPF, FHPF, FBPF, and FBSF of order n þ ug B n- (s) Butterworth polynomials (a) current mode topology, (b) voltage mode topology

25 .6 Fractional-Order Filters of Order n þ 37 Table.0 Values of scaling factors G i for realizing FLPF, FHPF, FBPF, and FBSF in Fig..5 of order n þ Filter G 3 G G G 0 FLPF 0 κ 0 κ 0 κ 0 FHPF κ κ κ FBPF 0 κ κ 3 κ κ 3 κ κ FBSF κ κ ð þ κ Þ κ ð þ κ Þ κ κ The realized transfer function is that given in (.64). Comparing the coefficients of (.64) with these of FLPF, FHPF, and FBSF it is derived that, under the assumption that nþ ¼, the design equations about the time-constants τ j ( j ¼,,..., n þ ) of all the filters are given in (.65). The corresponding design equations for the scaling factors G i (i ¼ 0,...,3) are summarized in Table.0. H nþ ðþ¼ s G 3 τ τ n s 3 þ G τ τ n s þ G τ τ nþ s þ G 0 τ τ nþ s nþ þ τ s nþ þ τ τ s n þþ τ τ τ nþ τ j ¼ nþ3 j nþ j τ ð:64þ ð:65þ In case time-constants are to be expressed as a function of the desired half-power frequency ( h ), then the above equation could be modified as τ j ¼ nþ3 j h ð:66þ nþ j Taking into account the fact that all the aforementioned procedure is somewhat complicated due to the algebraic calculation of the coefficients κ especially in case of high-order filters. Thus, an alternative solution for realizing high-order fractional filters is through the cascade connection of þ and n order filters, which is expressed in the following equation as H nþ ðþ¼h s þ ðþh s n ðþ s ð:67þ where H n (s) ¼ / B n (s) is the transfer function of the n order Butterworth filter, the derivation of which is a trivial procedure. A suitable topology for this purpose is depicted in Fig..6, from which is obvious that having available the topology of an þ order filter and an integerorder filter of an n order filter, it is readily obtained that one additional step is required for realizing an n þ order fractional filter.

26 38 Procedure for Designing Fractional-Order Filters Fig..6 FBD for realizing FLPF, FHPF, FBPF, and FBSF of order n þ ug (n-) Butterworth filter (a) current-mode topology, (b) voltage-mode topology The gain response of the filter is that given in (.68), where and are the 3 db frequencies of the þ and n order filters, respectively. jh nþ ðþj ¼ rffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi rffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffiffi þ ð Þ ðn Þ þ þ Performing a routine algebraic procedure it is derived from (.68) that h Þ ðþþ h Þ ðn Þ þ h Þ ðn Þ þ h Þ ðþþ ¼ 0 ð:68þ ð:69þ Taking into account that and are selected to be the same and equal to, then (.69) is simplified to (.6)..7 Summary Fractional-order differentiation/integrator blocks and fractional order generalized filters have been realized in this section, through the utilization of the CFE, which enables the opportunity of realizing all the aforementioned topologies through integer-order counterparts which is a trivial procedure. Each category has been performed by ug a general form, offering the capability of implementing various types of transfer functions without modifying their core, which is very important from the design flexibility point of view. Having available all this procedure, then it is easy to realize every kind of the aforementioned fractional-order circuits ug the suitable or desirable way of implementing the integer-order counterparts (i.e., integrators), which thereafter depends on the designer choice. They could be realized either ug a current mode procedure ug for example current-mirrors, or a voltage mode ug OTAs. Some of these implementations will be described and realized in detail in the next sessions.

27 References 39 References. Abdelliche, F., Charef, A.: R-peak detection Ug a complex fractional wavelet. In: Proceedings of the IEEE International Conference on Electrical and Electronics Engineering (ELECO), pp (009). Abdelliche, F., Charef, A., Talbi, M., Benmalek, M.: A fractional wave-let for QRS detection. IEEE Inf. Commun. Technol. (), (006) 3. Ferdi, Y., Hebeuval, J., Charef, A., Boucheham, B.: R wave detection ug fractional digital differentiation. ITBMRBM. 4(5 6), (003) 4. Goutas, A., Ferdi, Y., Herbeuval, J.P., Boudraa, M., Boucheham, B.: Digital fractional order differentiation-based algorithm for P and T-waves detection and delineation. Int. Arab. J. Inf. Technol. 6(), 7 3 (005) 5. Benmalek, M., Charef, A.: Digital fractional order operators for R-wave detection in electrocardiogram signal. IET Signal Process. 3(5), (009) 6. Radwan, A., Soliman, A., Elwakil, A.: First-order filters generalized to the fractional domain. J. Circuits Syst. Comput. 7(), (008) 7. Tsirimokou, G., Psychalinos, C.: Ultra-low voltage fractional-order differentiator and integrator topologies: an application for handling noisy ECGs. Analog Integr. Circ. Sig. Process. 8 (), (04) 8. Maundy, B., Elwakil, A., Freeborn, T.: On the practical realization of higher-order filters with fractional stepping. Signal Process. 9(3), (0) 9. Freeborn, T., Maundy, B., Elwakil, A.: Field programmable analogue array implementation of fractional step filters. IET Circuits Devices Syst. 4(6), (00) 0. Ortigueira, M.: An introduction to the fractional continuous-time linear systems: the st century systems. IEEE Circuits Syst. Mag. 8(3), 9 6 (008). Elwakil, A.: Fractional-order circuits and systems: an emerging interdisciplinary research area. IEEE Circuits Syst. Mag. 0(4), (00). Biswas, K., Sen, S., Dutta, P.: Realization of a constant phase element and its performance study in a differentiator circuit. IEEE Trans. Circuits Syst. II Express Briefs. 53(9), (006) 3. Krishna, B., Reddy, K.: Active and passive realization of fractance device of order ½. Act. Passive Electron. Compon. 008, Article ID 3694 (008) 4. Radwan, A., Elwakil, A., Soliman, A.: On the generalization of second-order filters to the fractional-order domain. J. Circuits Syst. Comput. 8(), (009) 5. Freeborn, T., Maundy, B., Elwakil, A.: Towards the realization of fractional step filters. In: Proceedings of IEEE International Symposium on Circuits and Systems (ISCAS), pp (00) 6. Mondal, D., Biswas, K.: Performance study of fractional order integra-tor ug glecomponent fractional order element. IET Circuits Devices Syst. 5(4), (0) 7. Radwan, A., Salama, K.: Fractional-order RC and RL circuits. Circuits Syst. Signal Process. 3 (6), (0) 8. Ahmadi, P., Maundy, B., Elwakil, A., Belostotski, L.: High-quality fac-tor asymmetric-slope band-pass filters: a fractional-order capacitor approach. IET Circuits Devices Syst. 6(3), (0) 9. Ali, A., Radwan, A., Soliman, A.: Fractional order Butterworth filter: active and passive realizations. IEEE J. Emerging Sel. Top. Circuits Syst. 3(3), (03)

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